Dear reader - the following is the TIE paper FINALLY published. Still a few glitches in the download of this but the most of it's here. Please note - this is authored by R.A Ainslie, H.W Gramm, G.A Lettenmaier, A.Palise, A. Gardiner, D Martin, S. Windisch. IT HAS NOT BEEN PUBLISHED BY TIE and I am simply referencing it here as the work done by Open Source.
As a reminder it is the work of collaborators and in terms of copyright pertaining to a collaboration ALL authers are entitled to use, publish or distribute this work individually, as they require. In the event that anyone get financial rewards for publishing then those rewards must be shared. And a further reminder - I'm therefore legally permitted to publish this here on my blog just in case Harvey or Glenn again try and get this removed by unreasonable claims of plagiarism.
Kindest regards,
Rosemary
Evaluation of power transients generated to improve performance coefficient of resistive heating systems |
Abstract— This experiment is designed to test the predictions of a thesis that determines material hidden properties of charge in circuit components. A MOSFET switching circuit is applied in series with an inductive resistive load and an interactively tuned duty cycle on the gate then enables an aperiodic, self oscillating frequency. Subject to overlying harmonics this is seen to improve the circuit’s coefficient of performance above four. The thesis proposes that this level of efficiency is due to the induced transients where the resultant current flow emanates from the circuit components. It is proposed that these have an alternate material source of charge to that of the supply. This energy is further proposed to be the source of the anomalous heat signatures as the circuit components enable this charge flow through the battery supply thereby also enabling a conservation of charge.
Index Terms— Transient analysis, Heating, MOSFET circuits, Resistive circuits
I. Introduction
THE following tests were designed to evaluate a thesis that predicted anomalous heat signatures on an inductive resistor placed in series with a switching circuit. The thesis is developed from a non classical magnetic field model but a full description of this falls outside the scope of this submission. What is pertinent here is some overview of that thesis as it applies to current flow. The following paragraph is intended as a broad brushstroke description of this and is further clarified as described in the Appendix I.
The model proposes that charge has the property of mass with the material properties of velocities and thermal capacities associated with that mass. These particles do not conform to the standard model and remain hidden within three dimensional solid or liquid objects or amalgams. They are extraneous to the atom itself and only interact with the atomic energy levels that, in turn, comprise independent fields of the same fundamental particle. These extraneous fields are responsible for the bound condition of the amalgam. This interaction between the fields and the atoms’ energy levels results in a balanced distribution of charge throughout the amalgam. Measurable voltage reflects a transitional state of imbalance throughout these binding fields that, subject to circuit conditions, then move that charge through available conductive and inductive paths to reestablish a charge balance. In effect the circuit components that enable the flow of charge from a supply source are, themselves able to generate a flow of current depending on the strength of that applied potential difference and the material properties of the circuit components. Therefore both inductive and conductive circuit components have a potential to generate current flow in line with Inductive Laws.
Classical assumption requires an equivalence in the transfer of electric energy based as it is on the concept of a single supply source. Therefore voltage measured away from the supply on circuit components is seen to be stored energy delivered during closed circuit conditions of a switching cycle. The distinction is drawn that if indeed, the circuit components are themselves able to generate a current flow from potential gradients, then under open circuit conditions, that energy may be added to the sum of the energy on the circuit thereby exceeding the limit of energy available from the supply. Therefore if more energy is measured to be dissipated at a load than is delivered by the supply, then that evidence will be consistent with this thesis. The experimental evidence does indeed, conform to this prediction.
This submission details the experimental apparatus, the applied measurements protocol and the data from a test that is designed to adequately assess the data as it relates to the thesis. It is considered that this submission of the experimental results will allow a wide dissemination both of the experiment and some consideration of questions relating to these anomalies, as being preferred and required.
The circuit is designed to enable a secondary, current flow that is induced from the collapsing fields over the resistor during the ‘off’ period of the duty cycle as a result of counter electromotive force (CEMF). This induces a flow of current in anti phase to the initial current from the source and this is seen to return to the battery supply source to recharge it. The performance coefficient is enhanced through an applied duty cycle that allows the circuit components to oscillate at a naturally recurring frequency. This is referred to herein, as a preferred mode of oscillation which, in turn, results in an aperiodic, self-regulated, resonating frequency. Distinctive harmonics are evident in the waveform and these are seen to be a required condition to the circuit’s enhanced performance as it relates to the efficiency of the recharge cycle over the battery. However the precise parameters of the duty cycle, determined by adjustment of the potentiometer at the gate of the MOSFET transistor, are found to be both critical and elusive.
The fact that these benefits to an enhanced coefficient may have been overlooked under usual applications can be attributed to the narrowness of the range required for this setting. Under usual applications such aperiodicity is considered undesirable and therefore systematically factored out of standard switched applications.
Also included is a discussion on ‘meshed currents’ that are evident and a detailed account of the data analysis that was applied to all measurements.
A series of related tests are appended that variously record the progress of the applied test parameters and the improved methods of measurements as the knowledge of the application unfolded. This schedule includes an evaluation of the inductance required on the load resistor to optimize the effect, as well as an evaluation of the comparative diameters of that resistor to determine optimized conditions. Other tests include the measurements that were performed to address a variety of concerns including grounding problems, voltage differentials and applied high frequencies without the required harmonics. These have been appended, together with an overview of the thesis relating to this effect, for both purposes of record and to afford a fuller evaluation as required.
The test that is described herein has results that appear to be consistent with the predictions of that thesis. The returning current from CEMF is seen to reduce the battery discharge rate while sustaining a higher level of energy dissipated at the load. This has a resulting advantage to the coefficient of performance. Indeed, the actual measurements indicate a potential for an absolute conservation of charge at the supply. The conclusions to the tests include a broad discussion of the potential of this technology and indicate a need for expert evaluation of both the results and the theoretical paradigms that predicted the results.
II. Experiment
A. Description
The experiment described herein is one example taken from more than 14 individual tests. All of the tests demonstrate various aspects of the preferred operation as well as exposing specific characteristics that relate to the circuit being evaluated. The test that is chosen for full description is shown to comply with a required and stringent measurement analysis as the standards of testing progressed throughout the test period.
The positive terminal of a 24 volt battery bank is applied in series with a 10 Ohm wire wound inductive resistive load, an N-Channel Power MOSFET [1] (Q1) Fig. 1, and a 0.25 Ohm shunt resistor (R2) Fig. 1. A separate 12 volt battery supplies a 555 (U1) Fig. 1 switching circuit which is capable of variable duty cycles and frequency adjustments. Q1 was chosen with an
Fig. 1. MOSFET Heater Circuit – R7 and R4 is for duty cycle adjustment. R1 is for adjusting to preferred mode of oscillation
avalanche protection body diode [2] feature that enables conventional reverse current flow during the off period of the duty cycle and protects against high voltage CEMF.
U1 drives the gate [3] of Q1 directly through a precision variable resistor (R1) Fig. 1. Specific adjustment of R1 and the variable resistors R4, and R7 shown in Fig. 1 enables a preferred mode of oscillation that overrides the predetermined frequency and duty cycle. The fundamental and harmonic waveforms that result vary greatly from one cycle to another. The transient voltages that are deliberately generated, then compound this variation. The duty cycle is adjusted using R4 and R7 whereas R1 is critical to enabling a preferred self oscillation.
TABLE I
CIRCUIT COMPONETS
Part | Description |
C1 | 0.01 µF Capacitor |
C2 | 0.001 µF Capacitor |
C3 | 0.047µF Capacitor |
C4 | 100 µF Capacitor |
D1 | 1N4007 Diode |
D2 | 1N4148 Diode (1N914) |
D3 | 1N4148 Diode (1N914) |
Q1 | IRFPG50 HEXFET MOSFET, International Rectifier |
R1 | 100 Ohm Potentiometer 10-Turn 2-watt, Vishay Spectrol #SP534 |
R2 | 0.25 Ohm 30 watt 1% non-Inductive Resistor, Caddock Electronics Inc. #MP930 |
R3 | 10 Ohm + - 5% Custom Prototype wire wound “Quantum” Load Resistor |
R4 | 2K Ohm Potentiometer 10-Turn 2-watt, Vishay Spectrol #SP534 |
R5 | 110 Ohm 1/8 watt Resistor |
R6 | 330 Ohm 1/8 watt Resistor |
R7 | 10K Ohm Potentiometer 10-Turn 2-watt, Vishay Spectrol #SP534 |
R8 | 330 Ohm 1/8 watt Resistor |
U1 | NE 555N Timer, Fairchild Semiconductor |
V1 | 12 V “Liquid” Lead Acid Battery (Qty-2) Exide, GT-H, Group U1, 12 aH (24aH - total) |
V2 | 12 V “Gel” Lead Acid Battery CSB Battery Company, LTD., GP 1270 F2, 7 aH |
Names of circuit component manufacturers are provided where known.
B. Equipment and Connections
A Tektronix TDS3054C Digital Phosphor Oscilloscope [4] was provided for these tests offering 500MHz bandwidth and digital storage capability able to data capture 10K records at any one time period. Four probes are used as outlined in Fig. 2 and detailed in section D herein. Also used is a Fluke 87 True-RMS DMM [5] across the 24V battery bank as a visual guide during the tuning process.
Fig. 2. Wiring Diagram showing probe locations and wire sizes
The scope probes were also checked relative to each other for excessive relative phase discrepancies when connected to the same signal source as indicated in Fig. 3. The signal source was provided by a Protek 2MHz function generator set to output a square wave with an instrument specified rise time of approximately 80ns.
Fig. 3. The four scope traces show the relative phase differences when all four probes are connected to the same square wave signal source
A Fluke 62 Mini Infrared Thermometer [6] was used for all temperature measurements and was held at the distance needed to ensure proper readings without background interference. For example, the 3.2cm load resistor required a measurement distance of no more than 32cm to ensure the reception area remained within the diameter of the resistor according to the spot ratio of 10:1. The ambient temperature was always measured at least one meter from the components radiating thermal energy.
A Velleman HQ PS3003 [7] DC regulated power supply was used for obtaining the baseline heat profile for the resistor under test. The output voltage of the PS3003 was verified to be within factory specification of +/- 1% +/- 2 digits using the Fluke 87 [5] with all voltage readings being identical on both pieces of equipment accurate to two decimal places.
A. Preferred mode of oscillation
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To establish this preferred mode of oscillation involves several interactive readings and a trained eye in order to properly adjust R1. The procedure towards obtaining the preferred mode of oscillation is relatively straightforward but somewhat arduous and requires a developed skill. While monitoring the four waveforms on the oscilloscope [4], the voltage across the current sensing resistor is monitored on Channel one (CH1) with the mean value displayed in the right margin. R1 is then adjusted to produce the lowest mean value while monitoring the 24V battery voltage with the Fluke [5].
When the circuit is operating outside the desired parameters the battery voltage drops noticeably due to the power drain. The adjustment is sought that causes a stabilization or slight increase in battery voltage. It has been determined that there is an observable delay between the signal from U1 to turn off Q1 and the inductive collapse of the magnetic field associated with the load resistor R3. This delay is desirable and necessary to produce the preferred mode of oscillation. In the tests this delay was typically around 350ns. The inductive collapse of the magnetic field associated with R3 is monitored on Channel two (CH2) and is seen as a voltage increase at the drain pin of Q1. The drive signal is monitored on Channel three (CH3) as the voltage measured on pin 3 of U1. The time between the falling edge of CH3 and the rising edge of CH2 is the delay being discussed. An additional parameter that is not critical but preferred is that there is good amplitude on the CH2 signal. When all four of these conditions are found the circuit is in the preferred mode of oscillation offering an improved performance. Tuning the preferred mode of oscillation with the single adjustment, R1, is no easy task due to the interactive and recursive nature of the aperiodic frequencies and their respective subharmonics.
A. Data Analysis
In evaluating the data obtained at regular intervals it was observed that the resolution was greater at the faster time base but this was at the expense of the quantity of cycles required for a good average. The oscilloscope [4] vertical settings were set for voltage inputs while the horizontal settings were set to the desired time base. Using the 2V/div vertical scale with 40µs/div horizontal provided two decimal places or 10mv resolution and with 2µs/div provided six decimal places of resolution or 1µV. Similarly, using the 100V/div setting provided us with integer values or 1V resolution in the 40µs/div setting, and four decimal places or 100 µV in the 2µs/div setting. In the preferred mode of operation a typical 20µs period, that is one full screen capture at 2µs/div, would capture approximately 6 to 10 complete cycles. The oscilloscope provided excellent sample resolution of 10k samples per screen capture and this ensured accurate data collection for the frequencies observed. The entire spectrum is aperiodic in the preferred mode of operation with a fundamental frequency usually near 3.5 kHz but ranging from 140 kHz beyond 500 kHz and various subharmonics which are observed to modulate the amplitude of the fundamental in superposition [8]. It was determined that approximately 140µs of data would contain about six intervals of the superimposed signal and therefore the 400µs captures of 40µs/div would be sufficient to provide a good average of operation. Analysis was performed for each individual capture as well as an average of the composite of each 40µs/div and 2µs/div. The data captures at each six minute interval during the one hour test were taken in that order with just a few seconds in between each capture limited only by the physical need to set the oscilloscope to the desired horizontal time base setting as the scripting features were not used for this process.
The data comprises the capture of four channels of voltage measurements and a relative time marker. The associated points of measurement can be seen in Fig 2 as follows: Channel one (CH1) is the instantaneous voltage measured across R2 at the junction of R2 and the 1.9cm (0.75in) bare wire connection to the source pin of Q1. Channel two (CH2) is the instantaneous voltage measured at the drain pin of Q1. Channel three (CH3) is the instantaneous voltage measured at the timer NE555-PIN 3. Channel four (CH4) is the instantaneous voltage measured at the Voltage Source Measurement Location on the Positive Feed Wire (See Fig. 2). The objective of the analysis was to determine the average source power delivered to the load so as to compare that value to the required baseline for the same relative temperature of the load. In this way it could be determined if the circuit was providing an improvement when compared to the standard DC power baseline.
The data imported into the spreadsheets represented columns A - E for Time Marker, CH1, CH2, CH3 and CH4 respectively. A new column G was used for the power calculation using the spreadsheet formula E:x*(B:x/0.25) where E and B are the column references, x is the row number and 0.25 represents the resistance of the current sensing resistor (R2) in ohms. This formula is copied to all rows in column G and represents the power formula P=EI where E is the CH4 voltage and I is the instantaneous voltage of CH1 divided by the resistance of R2. A comparison was made between an average of all the rows of data for each column and just those rows which represented complete cycles with no significant difference. Also, an application of the Simpson’s Rule [9] was made to determine if the parabolic treatment of the waveforms would offer any substantial difference as compared to the spreadsheet average function (2). The formula used relates to the composite Simpson’s Rule in the form (1) where n is even and ∆x = (b - a)/n.
(1)
The total number of data rows in the spreadsheet range from row 2 to row 10001, therefore only 9999 rows could be used for the approximate integration using the Simpson’s Rule. The difference from the spreadsheet average function and the Simpson’s Rule approximate integration was within 0.04W for 21 of the collections with the 22nd collection being 0.05W difference. Table II shows the source power average and Simpson’s Rule Integration for each sheet from the test which consisted of 22 data dumps taken at 6 minute intervals over a one hour period. At each interval two data dumps were recorded; one for 40µs/div and one for 2µs/div. The time between a 40µs/div data dump and a 2µs data dump for any given interval is only a few seconds. The temperature recordings as they relate to each sheet are found in Fig. 4 and
the baseline chart is found in Table III.
TABLE II
Source Power Averages and Integration
Sheet Number | AVG | SRIa |
TEK00000 | 0.00 | 0.01 |
TEK00001 | -1.05 | -1.06 |
TEK00002 | 3.60 | 3.61 |
TEK00003 | 3.98 | 4.00 |
TEK00004 | 2.96 | 2.93 |
TEK00005 | 5.59 | 5.58 |
TEK00006 | -0.87 | -0.89 |
TEK00007 | -0.44 | -0.40 |
TEK00008 | 0.39 | 0.39 |
TEK00009 | -1.17 | -1.12 |
TEK00010 | 4.92 | 4.88 |
TEK00011 | -1.59 | -1.55 |
TEK00012 | -0.17 | -0.20 |
TEK00013 | -0.41 | -0.41 |
TEK00014 | 0.09 | 0.10 |
TEK00015 | 5.12 | 5.15 |
TEK00016 | -0.71 | -0.71 |
TEK00017 | 2.39 | 2.39 |
TEK00018 | -0.42 | -0.44 |
TEK00019 | 0.13 | 0.15 |
TEK00020 | -0.12 | -0.13 |
TEK00021 | 6.45 | 6.40 |
AVERAGES | 1.30 | 1.30 |
aSimpson’s Rule Integration
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TABLE III
Schedule of Custom Load Resistor Temperature Baseline
VOLTS DC | AMPS | °F | AMBIENT | DIFFERENCE | WATTS |
4.8 | 0.50 | 107 | 73.5 | 33.50 | 2.40 |
5.0 | 0.52 | 110 | 73.8 | 36.20 | 2.60 |
5.2 | 0.54 | 114 | 73.9 | 40.10 | 2.81 |
5.4 | 0.56 | 116 | 73.8 | 42.20 | 3.02 |
5.6 | 0.58 | 118 | 73.6 | 44.40 | 3.25 |
5.8 | 0.60 | 120 | 73.8 | 46.20 | 3.48 |
6.0 | 0.62 | 122 | 73.9 | 48.10 | 3.72 |
6.2 | 0.64 | 125 | 73.8 | 51.20 | 3.97 |
6.4 | 0.66 | 128 | 73.9 | 54.10 | 4.22 |
6.6 | 0.68 | 131 | 74.1 | 56.90 | 4.49 |
6.8 | 0.70 | 134 | 74.1 | 59.90 | 4.76 |
7.0 | 0.72 | 137 | 74.2 | 62.80 | 5.04 |
7.2 | 0.74 | 139 | 74.3 | 64.70 | 5.33 |
7.4 | 0.76 | 142 | 74.7 | 67.30 | 5.63 |
7.6 | 0.78 | 146 | 74.9 | 71.10 | 5.93 |
7.8 | 0.80 | 148 | 75.0 | 73.00 | 6.24 |
8.0 | 0.82 | 153 | 75.0 | 78.00 | 6.56 |
8.2 | 0.84 | 155 | 74.9 | 80.10 | 6.89 |
8.4 | 0.86 | 157 | 74.5 | 82.10 | 7.22 |
8.6 | 0.88 | 159 | 74.5 | 84.50 | 7.57 |
8.8 | 0.90 | 164 | 74.6 | 89.40 | 7.92 |
Current flow to and from the battery was determined from the voltage waveform across the 0.25 Ohm non-inductive sense resistor (shunt) divided by its resistance. The use of that shunt minimizes the inaccuracies that relate to the measurement of impedance to an oscillating waveform. Typically, batteries are not able to deliver a negative current flow. Therefore, it was determined that current delivered by the battery would be the product of instantaneous voltage measured across the shunt divided by the resistance of the shunt measured above zero. Correspondingly, any current delivered back to the battery would be determined from the instantaneous voltage across the shunt divided by the shunt’s resistance, measured below zero. The net flow of current from the battery would be the difference between these two values.
To ensure that both positive and negative transitions were accurately recorded the oscilloscope was set to direct current (DC) coupling. Multiple data dumps of ten thousand samples each were stored and downloaded to spreadsheet for analysis. The equation applied in the analysis for source power determination was
, (2)
where V is the source voltage where measured, I is the current calculated at the shunt and X is the number of samples analyzed.
B. Energy Dissipated at Load Resistor
The inductive property of the load resistor was required to generate high voltage spikes during the off period of each switching cycle. Also, the impedance varies with frequency and temperature which makes it difficult to determine the accurate instantaneous impedance of the load resistor at any given moment. These conditions caused protracted discussion on the accuracy of measurement related to current phase lag within the inductive component of the load. To address these concerns it was agreed to confine the measurement of power dissipated to caloric values as proof of dissipated energy.
Measurement of the load resistor temperature was enabled through the use of an Infra Red Thermometer chosen because it is not easily affected by electromagnetic interference. The readings were recorded from the digital display in degrees Fahrenheit and were conducted in a draft free environment. Ambient room temperature was recorded consecutively. Temperature measurements were also taken of R2 and Q1 and the results recorded, as represented on the attached schedule. The difference between ambient room temperature and the load resistor was considered to represent the actual caloric value under test conditions.
The heat profile of the load resistor was manually calibrated using a variable power supply source. The supply was increased from 4.8 volts to 8.8 volts in increments of 0.2 volts each. All voltages were verified by reference to independent readings taken across the resistor with a Fluke [4] multimeter. At each interval the amperage was recorded and the power was then calculated as V*I. When stabilized after each interval the resistor temperature and the ambient temperature were recorded. The entire calibration was performed in a draft free environment. Table III shows the results of the calibration.
II. Mesh Currents
This paper would not be complete without some discussion regarding the interactions between the timer circuit and the heating circuit. Each circuit has an independent supply source and it was necessary to consider whether the observed improvements could be attributed to a power exchange from the timer supply to the heating load. While a DC approach to this concern is relatively straight forward as there is a DC barrier between the Q1 gate and the other two circuit paths via the drain and source pins, it is also considered that there is an AC path or Pulsed DC path through this barrier. The various capacitances and even the stored energy in the inductances of the leads in Q1 can work as charge carriers passing energy back and forth across that barrier. U1 can source and sink a maximum 200mA and has a maximum operating temperature of 70°C [10]. Since this is the only conductive path for current to flow in, these parameters limit how much power can be passed via this pathway. In addition, the 2800pF Ciss [11] of Q1 represents a capacitive reactance of around 160 ohms at the fundamental frequency. Also, there are a few ohms of resistance in R1 as part of the combined limit. Therefore if one were to conservatively calculate the resistance of R1 to be only 2 ohms and if one were to also discount any reactive impedance of the load resistor and take it at its resistive value of 10 Ohms giving 12 Ohms to add to the 160 Ohm impedance caused by the capacitive reactance the result is a conservative resistance of 172 Ohms. Now if one was then able to pass the maximum allowed current of 200mA through that resistance, 34.4V would then be needed. Therefore, the maximum instantaneous power that could be transferred through that path would be approximately 6.8W. So in order to answer the question as to whether this could in fact occur it was deemed necessary to perform an auxiliary test wherein a second current sensing resistor was placed in the interconnect path at the Voltage Source reference point. With the understanding that all of the current sourced by the timer circuit battery must return to that battery and the interconnect being the only path by which it could occur it was thought that any power being transferred into the gate must then return via the interconnect wire. For this test the probe was removed from the U1 Pin 3 position and placed on the secondary current sensing resistor lead connected to the interconnect wire identified in Fig 2 as a possible shared current path. The circuit was run in its preferred mode of operation and a data dump was performed using the 2µs/div time base. It was expected that some portion of the R3 charging current would find its way through that path in a parallel manner bypassing the R2 sensing resistor. The expectation therefore was the need to add this current to the existing current to get a full picture of the operation. Surprisingly, the net value of the current running in that leg was negative. Nevertheless an integration of both currents was necessary to get the real picture. The results indicate that a mesh current [12] flows through the source pin of Q1 and actually inflates the current reading by a value of a little under 1W. This means that the documented improvements are conservative by that quantity. As far as any currents being supplied by the timer circuit and flowing through the load resistor and 24V battery bank, that current would have been present in the same interconnect wire on its return path. Even if all the current found in this case was attributed to such an unlikely path it still falls short of the observed performance increases. Therefore it is concluded that the timer battery is not the source of the improvements.
III. Discussion
As the overriding purpose of the test is to evaluate the advantages in applying that second cycle from a switching circuit, a battery supply source was used. It is understood that a battery cannot deliver energy in open circuit conditions and any energy evident to the circuit during the off period would therefore be sourced away from that supply. What was evident in the voltage waveform, as measured at the source, was that the spike at the drain was able to recharge the battery. This spike results from the collapsing fields in the inductive load resistor. The extent of that recharge was also evident in the reading of a voltmeter placed directly across the battery terminals.
Battery performance requires separate and specific evaluation disciplines and it was considered to be outside the scope of this paper. Therefore those records of duration and voltage levels were simply included as a reference. It is to be noted that the actual test results indicated a small but nonetheless, measurable net loss to the battery voltage notwithstanding the evidence of zero net loss in some measurements. This may be attributed to the evident and occasional loss of the overlying harmonics during circuit operation, which loss is seen to diminish efficiency.
Also of concern is that, in the initial tests, the point of the Source Power reference ground used for the probes and timer interconnect point were positioned about 15cm away from the shunt. This then may have the apparent effect as that of a 100nH inductor thereby increasing the overall amplitude of the shunt voltage measurements. Therefore, measurements of this test included the repositioning of this reference point directly onto the shunt lead. Interestingly, this did reduce the overall amplitude of that measured signal which was evident when the vertical setting on the oscilloscope was reduced to 1V/div. However the net mean voltage reading actually dropped indicating a greater improvement in performance over those earlier tests.
Initial tests also included the use of a wire wound shunt with some inductance associated with that winding. To obviate this, the test detailed herein was done with a replacement non-inductive shunt as detailed in the Components schedule. But there was very little evidence of measurements difference between these two components.
Also of interest is the fact that the circuit was able to run for extended periods at less than half the optimum charged condition of the battery while still dissipating energy at the load resistor. The indications here were that the resonating condition of the supply and the inductive components of the resistor were able to sustain a potential difference to enable a continual exchange. This test is only referenced to encourage further investigation of this effect.
This test indicated a marginal net loss to the voltage of the source batteries notwithstanding periods of an evident recharge. This is in line with the thesis and is variously attributed to the momentary and occasional loss of the signature harmonics that are required for optimization of results. But the evidence is that, subject to the sustainability of those harmonics, the theoretical indications are that battery discharge can be obviated. This directs attention to the need for some manufactured means of sustaining those harmonics that may be required in optimized conditions of application and, in turn, requires further research.
Apart from the anomalous heat signatures developed over the resistive load is the evidence of anomalous waveforms that point to the simultaneous and alternate current paths that can be developed across a circuit. These paths have not been fully established and further emphasize the need for further study to determine some alternate principles to be incorporated into known paradigms to account for these effects. Of interest is that the waveforms are replicable in simulated programs, e.g. Spice. This suggests that classical algorithms can account for these electromagnetic interactions. However, phase shifts in current are not so easily modeled and the reality suggests a complex arrangement that manifests as an improvement in performance.
IV. Conclusion
It must be stressed that the weighted averaging of the data dumps taken from these tests, were applied to reach a conservative value of the power delivered by the battery supply source. There is more energy returned to the battery source than is measured across the shunt as referenced in the discussion on meshed currents. And the shunt and MOSFET both dissipated heat. But these were not included in the evaluation of the results, as the heat dissipated at the load exceeded thermodynamic constraints and was therefore considered sufficient as proof of the coefficient of performance required for this thesis and this claim.
There was also evidence of zero net loss in the integration of measurements on some of these results in line with the thesis, thereby pointing to the need for further development requirements to sustain this potential.
While these results may confront classical constraints as they relate to the transfer of energy, and as predicted in terms of the thesis it is hoped that these results may be considered or that mainstream explore alternate models to account for these effects. The evidence is that it is possible to partially or entirely conserve energy while developing anomalous heat signatures over resistive loads. This, in turn, points to the need to revise current applications to exploit this benefit which may then obviate some of the pollutant effects associated with energy generation.
It is hoped that publication of this paper will address the need for a wide dissemination of these benefits. This document may then serve as a foundation for a more systematic research into the study and development of these effects.
Appendix I
The following exercise is intended as a broad brushstroke description of the non classical properties of current flow that was tested in the experiment described herein.
The classical approach to current flow recognizes that charge motion is predominately that of electric charge. The aspect of this thesis that is considered appropriate to this submission relates to current flow. It proposes that current flow comprises the motion of magnetic charge which, in turn comprises elementary magnetic dipolar particles. In classical terms, these particles would align with Faraday’s Lines of Force and therefore the number of lines that exist through a particular real or imaginary surface, would still be represented as magnetic flux while the particles themselves, in distribution along those lines, represent the magnetic field.
It is proposed that these fields are extraneous to the atomic structure of matter and are thought to play a critical part in binding atoms and molecules into gross identifiable matter. Further, the particles obey an immutable imperative to move towards a condition of balance or zero net magnetic charge. Given a source material with an ionized charge imbalance which is measured as a potential difference, and given a closed circuit electromagnetic material path, these particles will return to the source material with the necessary charge to neutralize that imbalance.
Typical electronic circuits provide such material paths through the circuit components of which they are made which includes all conductors. During the passage of current flow through such closed circuitry it is proposed that the charge imbalance is transferred to those circuit components. The individual imbalances in each component and each conductor then seek balance according to that immutable imperative. In typical electronic circuitry, each component that has been ‘charged’ by this transfer, will either neutralize the charge internally, or influence a secondary current flow in anti-phase or opposite polarity to the first cycle.
While this is substantially in line with classical assumption as it relates to the transfer of charge, the distinction is drawn that the energy that is then transferred to such electromagnetic components, is able to regenerate a secondary cycle of current flow in line with electromagnetic laws. This energy is then not limited to the quotient of stored energy delivered during the first cycle and as presumed by classical theory. Instead it is dependent on the circuit component’s material characteristics and the means by which those materials balance a charge put upon them. Therefore there is a real energy potential in the secondary cycle which would reflect in a measured improvement to the performance coefficient of the circuit arrangement. This enhanced performance coefficient may be at the expense of the bonding of the material in the circuit components. In a worst case condition, this energy may be released as is observed in an exploding wire that is put under extreme charge conditions due to excessive current flow. In a best case condition, the energy is released gradually over time and results in fatigue to those components. This paper addresses an application of the gradual release.
Appendix II
The following schedule lists those tests that were conducted as they progressed to the test described herein. It provides a hyperlink to the original data for precise and detailed reference. They are appended in the interests of submitting a comprehensive reference to assist with further investigation of this circuit effect as required.
Test 1
This test was conducted on a standard commercial resistor (Stock, R3S) of 10 Ohm. No gains were evident.
Test 2
Load resistor specially manufactured (Custom, R3C) to assessed Quantum test specifications. No gains were evident.
Test 3
R3C used. First gains evident but records only partially completed test. First evidence of the required harmonics.
Test 4
R3C used. No gains evident and also the loss of the required harmonics.
Test 5
R3C used. Gains were evident together with evidence of the required harmonics.
Test 6
R3S used. No gains evident. Nor could the required signature harmonics be found.
Test 7
R3C used. Gains evident but actual power values exceeding the voltage constraints of the DPO. Test was terminated but does point to the feasibility of advantages at higher power output.
Test 8
R3C used. Circuit was now assessed as workable for the required effect. Therefore were alligator clips removed and all leads shortened and soldered. Gains were evident. Required harmonics was again evident.
Test 9
R3C used. Non-inductive precision shunt resistor replaced. Gains were evident.
Test 10
R3C used. Test 9 effectively re-run to improve on results. Gains were evident indicating no material difference in the voltage values between the inductive and non-inductive shunt.
Test 11
R3C used. This test was conducted over a one hour period with intensive sample capture to determine that the range of voltage across the shunt fell within acceptable levels.
Test 12
New resistor wound as a further attempt to duplicate the properties of the original Quantum Test. No gain observed and evident loss of the required harmonics.
References
[1] Duncan A. Grant and John Gowar, Power MOSFETs, Theory and Applications, Wiley-Interscience, 1989
[2] International Rectifier, HEXFET Power MOSFET Designer’s Manual, 2nd ed. vol. 3, El Segundo, CA: 1995, pp. 1575-1581
[3] International Rectifier, HEXFET Power MOSFET Designer’s Manual, 2nd ed. vol. 3, El Segundo, CA: 1995, pp. 1541-1566
[4] Tektronix TDS3054C 500 MHz 4 Channel Digital Phosphor Oscilloscope Data Sheet [online], Available: http://www2.tek.com/cmsreplive/psrep/13406/41W_12482_17_2009.07.16.16.00.09_13406_EN.pdf
[5] Fluke 87 True-RMS Multimeter User Manual [Online]. Available: http://assets.fluke.com/manuals/87______umeng0800.pdf
[6] Fluke 62 Mini Infrared Thermometer Information Site, [online] Available: http://us.fluke.com/usen/products/Fluke+62.htm
[7] Velleman HQ PS3003 Users Manual, [online] Available: http://www.designnotes.com/downloads/PS3003U_Manual.pdf
[8] Edward J. Ross, Professional Electrical/Electronic Engineer’s License Study Guide, 1st ed. Blue Ridge Summit, PA: Tab Books, 1977, page 329
[9] James Stewart, Calculus Early Transcendentals, 5th ed. Belmont, CA: Thomson Brooks/Cole, pp. 522 - 524
[10] The Linear Control Circuits Data Book for Design Engineers, Texas Instruments Incorporated, 2nd ed., 1980, pp. 282-283.
[11] International Rectifier, HEXFET Power MOSFET Designer’s Manual, 2nd ed. vol. 3, El Segundo, CA: 1995, page 1116
[12] Edward J. Ross, Professional Electrical/Electronic Engineer’s License Study Guide, 1st ed. Blue Ridge Summit, PA: Tab Books, 1977, pp. 332-333
Fig. 1. MOSFET Heater Circuit – R7 and R4 is for duty cycle adjustment. R1 is for adjusting to preferred mode of oscillation
Fig. 2. Wiring Diagram showing probe locations and wire sizes
Fig. 3. The four scope traces show the relative phase differences when all four probes are connected to the same square wave signal source.
Fig. 4. Test13 Data: Load = R3, MOSFET = Q1, Shunt = R2, TEK columns = filenames of CSV files and PNG files respectively
Last Page
Fig. 5. Arrows in left margin mark zero volts for each channel. Note the compound frequency present in all waveforms.
Fig. 6. The Digital Phosphor technology helps to see the subharmonic modulation.
Fig. 7. Approximately 350ns after the high to low transition on CH3 (U1-Pin 3) the CEMF increase on CH2 (Q1-Drain) is observed. Note the residual charge present on CH3 after this partial transition and the slight increase in positive current on CH1 (R2) just prior to the CEMF increase.
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